Is ok. Here is the modeling technique, so you can do it yourself on the
330uH coil is:First work at LOW frequency, Rdc and that Inductance (at 1kHz). Take the physical dimensions. Try to find the 'window' size of the coil. Take a Wire Gauge Table of diameters/Areas. Assume a Stacking Factor of anywhere from 0.5 to 0.7 For small coils the SF can be fairly good, even 0.7 Also, assume a slightly 'less' diameter caused by stretching the wire. The tension placed when using these automatic winders slightly thins the wire, shifting the whole manufacturing range to smaller diameter and slightly higher resistance
Given the Rdc, find the length that makes that resistance for each gauge of wire near your estimation of wire gauges. Then wrap each length around the core, any core, These open cores are so poor you can use perms anywhere from 100 to 2000 and get the SAME inductance. Adjust the coil window to accomodate. Check to see if you 'filled' the window. If your guess fills the window, makes the right inductance, and makes physical sense as it lays on the bobbin, you're done with the basics. You have N and wire gauge.
Now you'll find you get close to the inductance, but what threw me off for a while, until I realized the logistics of making a connection to the coil, was that there had to be a 'half' turn. once I applied an 'adjustment', in this case, ((N-0.5)/N)^2 times the inductance of 21 THEN I got better than 1 % accuracy to match both the Rdc and the L, and used the bobbin up completely. My guess is Bournes just takes a bobbin and fills it with varying sizes of wire, and that's what makes up the family of available parts.
The skin effect was almost enough to destroy the Q of the coil going up in frequency, but not quite. The Rwinding went from 0.15 to over 4.5 ohms. I didn't see an easy way to model the perm of the core to get 'something' at
1kHz down to AIR at SRF of 45MHz. [I tried making the core slightly conductive which almost works] but since the Q was so bad at 7.96MHz, I assumed that by 45MHz the core was completely gone, so I used the 900nH air core value to calculate the 13.4pF parallel capacitance. As I said, got the basics can work from there.Anyway, that's the history of modeling the 4.7uH, 0.15ohm inductor. Now, you can do the same for your 330uH coil.
What really amazed me was how 'leaky' the fields were around that bobbin! To line up two cores that are only 2.5 mm tall by 3 mm diameter and separated by 2 mm of PCB and still get 0.084 coupling is pretty good. Or if NOT wanted, pretty bad. To prevent EMC problems, where that fields can so easily reach around your 'line filter'; I would NEVER use an open core. Well, unless you're willing to make your own shield, but why not just buy a closed core? I assumed NO conductive planes inside the PCB, because you wanted to have two cores communicate. You can go back and model the mounting WITH 1 oz copper layers. and see how much, at what frequency, gets blocked. You'll see the inductance drops, the Rwinding goes up and the coupling drops. You can write LUA script to do a series of analyses that will create a table of coupling values vs distance along the axis. You'll find you get a function that up close is proportional to inverse square of distance, then as you get further away its more like inverse cube of distance. Rule of thumb, at 3 diameters distance [or 3 of longest dimension] the fields are less than 1% of strongest field. Plus you can replace any complex structure with a simple magnetic dipole. In other words *if* you're far enough away, you can't tell anything about the magnetic structure, they all look alike.
Extra measurements? Try to characterize the part from low tohigh frequency Use whatever steps are easiest, but I prefer log steps, like, 1kHz, 3kHz
10kHz, etc finer or more coarse. At each data point characterize in terms of XL(f) and R(f) Later you can curve fit to smooth the data using octave, FREE Matlab clone. Then overlay plots using the FREE femm at the same frequencies. Working back and forth, get VERY close.