i need to sense the line voltage(duh!). My set-up is basically a two resistor divider across the L & N. The lower resistor is sized such that I get an approx. 4V peak-peak over it. A difference amplifier is connected across this resistor with a gain of approx. 1. Theoretically I'm suppose to get a replica of the mains voltage waveform. But, after building the circuit the output tends to be almost a square wave. Supply to the cct is +/-15v. The square wave peaks are hitting the supply rail. Any ideas how i could remedy this problem?
Make sure the schematic shows how the power supply to your amplifier is connected, grounded, etc. with respect to the power line it is monitoring.
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Paul Hovnanian mailto:Paul@Hovnanian.com
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Trust the computer industry to shorten the term "Year 2000" to Y2K.
It was this kind of thinking that got us in trouble in the first place.
-- Adrian Tyvand
Two dividers, yes, but with their low end tied to the measurement- circuit ground. Inexorx says he's seeking a replica of the AC line voltage, and an opto-coupler wouldn't be accurate. Nor do I think a transformer is necessary, provided certain precautions are taken. The AC power line can have short spikes to many thousands of volts, and it's important that the resistive divider circuit handle these without endangering the equipment or any users. Because the subject is complex, I'll not take the time to here to explore it, except to say that even a simple version should have many components.
So a transformer may be the easiest solution. If Inexorx needs an accurate output, he can lightly load the transformer with an RC to control high-frequency error and still enjoy a wideband low-voltage replica of the line voltage. For example, let's consider a Signal Transformer 241-3-24. This is a small 2.4VA split-bobbin type with excellent input-output isolation, but with the usual losses that we see in small, cheap transformers. We can analyze a simple model* to estimate its errors.
primary L_m, 4.6 H (low-level L-meter) primary L_m, 11.2 H (meas with 120Vac) primary Rdc, 372 ohms secondary L_ell, 25.1 mH secondary Rdc, 23.8 ohms open-circuit turns ratio, 0.254
First we'll consider the transformer's primary circuit, where its roughly 11H of (nonlinear) magnetizing inductance has a reactance of j4.27k ohms at 60Hz, which with 372 ohms of series resistance and 120V causes a 28mA magnetizing current at a calculated lag of -90+5 = -85 degrees to the 120 60Hz ac voltage. The transformer primary's R-L calculated vector loss is 0.4% at 60Hz, dropping to 0.09% at 120Hz, and less at higher harmonics. The 5-degree phase lag at 60Hz drops to 2.5 degrees at 120Hz and less above that.
Second, we'll consider the scene at the transformer's secondary. We can add a 100pF output capacitor, which with the 25mH leakage inductance will limit the high-frequency response to 100kHz, plus a 15k load resistor to damp the 100kHz L-C resonance. Multiply the primary's series copper resistance by 0.254^2 and add this to the secondary's resistance to get the transformer's Zout = 47.8 ohms. This means our 15k load will drop the output voltage by about 0.3%, which is fine given we don't know the turns ratio any better than than anyway.
Lord Inexorx will end up with an accurate voltage transformer up to 100kHz, with a small 0.4% drop-off at 60Hz (or an above-200Hz increase of 0.4%, if he prefers to think of it that way). This small error could be corrected with a few more parts.
Data from leakage-inductance threads on s.e.d., January, 1998. Try these threads, Message-ID: Message-ID:
Another wat to go is to use a large value resistor to feed current into a transformer working as a current-xformer. This lets you use a mechanically smaller transformer at the cost of having to burn off a little power in the resistor.
** All is sweetness and light until you factor in the effect of the "magnetising current " devil.
The I mag waveform is non-sine and hence NOT linearly proportional to input voltage - its reaches peak value close to each zero crossing causing significant distortion of the AC supply waveform appearing at the secondary.
With a low VA E-core, as mentioned by Win, this distortion is easily visible on a scope & amounts to circa 10% 3H.
The Imag current peak also causes a 15 to 20 degree lag in the zero crossings seen at the secondary - buggers up any zero crossing detector.
Also, the *actual* voltage ratio of the small E-core will vary with AC supply voltage - by at around 2 or 3% over the whole range.
All these nasties are easily avoided by using a toroidal type where Imag is Lilliputian.
Thank you for all the smart replies but i think i have left out something. I'm trying to do this for a 3-phase supply source. So the transformer solution though the best but would severely stretch the budget and the pcb real estate. Thanks all for sharing ur ideas & knowledge. Appreciate it.
Please forgive me for my ignorance but where do i get swcadii or a viewer for the aforementioned code. I've tried the newsgroup u have mentioned but the post is a replica of ur previous post here.
The transformer solution is still the best bet though. Have a look at using 1:1 (600:600 ohm) telecommunications transformers, (as used in modems, etc) connected across the lower-R in your attenuator. Cheap, small, 200Hz to 4KHz, and low THD.
I have used these for low-level 400Hz. The only problem is that they do have some sensitivity to external magnetic fields....... lay them out at right-angles to each other, and fit the whole pcb assembly into a steel box.
A quick, (easy to implement, but more expensive), solution is 3-off LEM LV 25-P isolated voltage transducers.
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